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All issues Volume 2 (2015) EPJ Applied Metamaterials, 2 (2015) 5 Full HTML
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EPJ Applied Metamaterials
Volume 2, 2015
Advanced Metamaterials in Microwaves, Optics and Mechanics
Article Number 5
Number of page(s) 6
DOI https://doi.org/10.1051/epjam/2015008
Published online 23 December 2015

© M. Barbuto et al., Published by EDP Sciences, 2015

Licence Creative CommonsThis is an Open Access article distributed under the terms of the Creative Commons Attribution License (http://creativecommons.org/licenses/by/4.0), which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

1 Introduction

Artificial electromagnetic materials, metamaterials, and metasurfaces have revolutionized the design of microwave and optical components, allowing to obtain better performances with respect to conventional solutions [1–8] or novel functionalities [9–14]. In particular, in the last years, there was a strong interest in the use of metamaterials for performing the manipulation of the electromagnetic waves. In the past, such ability has been achieved by using dielectric lenses, frequency selective surfaces and polarizers, but the additional degrees of freedom enabled by properly engineered metamaterials allows performing novel operation directly on the electromagnetic waves passing through them. For instance, the design flexibility of composite-right-left-handed transmission lines has been used in [15] for designing different signal processing systems, such as delay lines, pulse generators, and pulse-position modulators. Moreover, it has been shown that an array of waveguides, working at their cut-off frequency for emulating an epsilon-near-zero metamaterial [16, 17], can be used to perform a Fourier Transform of the electromagnetic signal propagating through them [18]. Finally, it has been proven that to perform some mathematical operations, such as convolution, integration and spatial differentiation, on an electromagnetic wave a metamaterial slab that is only one wavelength thick can be used [19].

However, the intrinsic frequency dispersion of 3D bulky metamaterials and the required engineered spatial dispersion makes the aforementioned solutions rather difficult to be realized. Moreover, in many cases losses are so high that the amplitude of the electromagnetic signal becomes impractical. In this framework, the authors have recently proposed to only use a single metamaterial-inspired electrically-small particle to perform signal manipulation. The advantage of such an approach is twofold: (i) the electromagnetic response of the signal manipulator overlaps the one of the metamaterial-inspired particle, and, thus, it can be easily predicted through an equivalent circuit model [20–22], (ii) being the particle electrically small, it can be easily integrated in conventional components for giving them new features.

Among the several signal manipulations that can be performed on an electromagnetic wave, we focus our attention on the filtering ones, which are typically performed by the front-end of a receiving system. In fact, any standard communication system employs filtering modules for removing the unwanted frequency components from the received signal. For instance, a band-rejection filter can be inserted in the front-end of the receiver to suppress interfering signals of other services operating within the same frequency band of the antenna. On the contrary, a band-pass filter can be used for reducing the background noise. Therefore, regardless of the type of the filter, the signal-to-noise ratio (SNR) significantly increases, improving the overall performances of the receiving antenna. In this framework, the possibility to have a highly efficient manipulation of the electromagnetic signal by using an extremely compact structure would represent an important achievement.

Although the integration of the antenna and the filters on a single microwave component has been proposed for planar printed antennas [23–26], where it is easy to integrate a conventional LC circuits or resonant particles acting as filters, little efforts have been made to embed filtering module directly inside horn antennas. Some attempts can be found in [27–29] based on the use of metal or dielectric posts or substrate integrated waveguide cavity frequency selective surface. However, they work only for one polarization and, due to their complex structure, need to be realized together with the antenna. On the other hand, the proposed metamaterial-inspired particles for signal manipulation can be easily integrated in any existing antenna system, as shown in the schematic block diagram of Figure 1. In particular, the integrated filter element, consisting of a single particle, is inserted between a regular waveguide and the horn antenna, which easily gains the filtering feature. This choice allows also keeping the system very compact and ensures the backward compatibility with the pre-existing communication systems. Moreover, the use of metamaterial-inspired particle can also add other advanced functionalities to the overall system such as polarization-control capabilities and non-reciprocity [30, 31].

thumbnail Figure 1.

Schematic block diagram of the proposed system.

In this paper, we review our recent work on metamaterial-inspired filtering modules that can be used in both transmitting and receiving self-filtering antennas [32–37]. In particular, we review a band-pass filtering module for linear polarization [34], a linear-to-circular polarization transformer with a band-pass behavior [35], and some notched-band filters [36, 37] that, consisting of compact resonant inclusions, can be easily integrated in horn antennas. Moreover, we show here how the use of different metamaterial-inspired particles allows performing different operations on the electromagnetic signals.

2 Band-pass filtering modules

Let us start by considering the band-pass feature of the proposed metamaterial-inspired particles. As discussed in Section 1, in a standard communication system employing horn antennas, a regular horn is connected to a feeding waveguide that is excited by a proper coaxial-to-waveguide transition. As it is well known, these components can support the propagation and radiation of electromagnetic signals over a broad frequency range. However, the signal to be received is typically band-limited (especially in satellite communications) and a band-pass filter can be used for selecting the band of interest and rejecting the out-of-band background noise. In the following, we present two metamaterial-inspired particles, which work for linear polarization (LP) and circular polarization (CP), respectively, comparing their performances.

2.1 Linear polarization

The first proposed particle, shown in Figure 2a, consists of a connected bi-omega particle placed through an aperture drilled in a metallic screen. In particular, the structure consists of two identical metallizations printed with opposite orientations on the two sides of a dielectric slab (GML 2032). Each metallizations can be seen as two individual bi-omega resonators connected through two metallic strips. The operating principle of such a particle as pass-band filter is based on the ability of the two identical bi-omega inclusions on the opposite side of the metallic screen to act as receiving and radiating electrically small antennas. At the resonant frequency, the energy captured by the first bi-omega from the TE10 propagating mode of the waveguide is transferred through the two metallic wires to the second bi-omega that, in turn, radiates and excites the same mode on the other side of the screen. It is now easy to understand that, if the particle is placed between the horn and the rectangular waveguide (as shown in Figure 2b), the antenna can perform a band-pass filtering process on the received signal.

thumbnail Figure 2.

Geometrical sketch of the band-pass filtering module working for linear polarization (a) and of the overall structure consisting of the filtering module inserted between a WR-62 waveguide connected to a pyramidal horn antenna (b).

In order to verify its effectiveness, the simulated reflection coefficient of the overall structure at the input port as a function of the normalized frequency is reported in Figure 4 (black solid line). It shows that a good impedance matching is achieved only in a narrow frequency band around the normalized resonant frequency, proving that the signal is not reflected back in that frequency band. In order to show that the energy is not absorbed by the particle, we report also the normalized realized gain in the main beam direction (Figure 5 – black solid line), which presents the same values of a regular horn antenna around the band-pass range and rapidly decreases moving away from it, confirming the efficient energy transfer and low loss introduced by the particle.

2.2 Circular polarization

The second proposed particle has been designed to operate on circular polarized signals. Such a particle needs to be properly designed because it is necessary that at least one symmetry plane orthogonal to the transverse section of the waveguide is present in order to radiate effectively both orthogonal components of the CP field. The connected bi-omega particle fails in this context because it is excited mainly by the magnetic component of the TE10 propagating mode in the rectangular waveguide, which has to be orthogonal to the bi-omega plane.

To this end, we have replaced the bi-omega particle with a Complementary Electrically Small Resonator (CESR), shown in Figure 3a, which has been inserted at the junction between a rectangular waveguide and a corrugated conical horn, as shown in Figure 3b. Properly designing the particle, we can convert the linear polarization of the TE10 mode in the waveguide into a circular one in the radiated field and vice-versa, in addition to filtering the received signal. In particular, the proposed device consists of two mutually orthogonal meander-line slot dipoles that, in order to obtain a circular polarization operation, are terminated with arrows that have slightly different dimensions. The filtering behavior is confirmed by the reflection coefficient and the realized gain of the overall structure, reported in Figures 4 and 5 (red dashed lines), respectively, as a function of the normalized frequency. The radiation of a circular polarized field, instead, is proven by the axial ratio, shown in Figure 6, which is below 3 dB around the resonant frequency of the particle.

thumbnail Figure 3.

Geometrical sketch of the band-pass filtering module working for circular polarization (a) and of the overall structure consisting of the filtering module inserted between a WR-62 waveguide connected to a corrugated conical horn antenna (b).

thumbnail Figure 4.

Reflection coefficient magnitude of a standard horn antenna (gray dash-dotted line) and of the same horn with a bi-omega particle (black solid line) or a CESR (red dashed line).

thumbnail Figure 5.

Normalized realized gain of a standard horn antenna (gray dash-dotted line) and of the same horn with a bi-omega particle (black solid line) or a CESR (red dashed line).

thumbnail Figure 6.

Axial ratio in the main beam direction of a horn antenna loaded with a CESR.

It is worth noticing that the common feature of the two proposed filtering modules for LP and CP fields is the use of a metallic screen that does not allow the propagation of the electromagnetic field, except in a narrow frequency range around the resonant frequency of the employed particle. As it will be discussed in the following section, this approach cannot be employed for designing band-stop filters that, in contrast, allow passing most frequencies unaltered while strongly attenuate those in a narrow frequency range.

3 Band-stop filtering modules

In this section, we present some particles that can be used for removing a narrowband interfering signal from the receiving spectrum of a horn antenna. A very simple method consists in using a single Split-Ring Resonator (SRR) placed directly inside the throat of a pyramidal horn antenna, as shown in Figure 7. Excited by the electromagnetic field in the horn, the SRR resonates and generates strong mismatch and loss phenomena around its resonant frequency, which can be predicted by equivalent circuit models [20, 21]. Please, note that, in order to have maximum interaction with the field, the SRR has to be parallel to the E-plane of the horn. In this way, the electric field will be parallel to the gaps of the SRR and the magnetic field will be normal to its plane, inducing the maximum possible currents on the metallic strips of the SRR. In contrast, moving away from its resonant frequency, the SRR does not interact anymore with the electromagnetic signal that is allowed to pass unaltered. This behavior is confirmed both by the reflection coefficient and the realized gain of the overall structure reported in Figures 8 and 9, respectively.

thumbnail Figure 7.

Geometrical sketch of the band-stop filtering modules consisting of a single SRR (a), a single MSRR (b), two coupled-SRRs (c) and of the overall structure consisting of the filtering module inserted between a WR-90 waveguide connected to a pyramidal horn antenna (d).

thumbnail Figure 8.

Reflection coefficient magnitude of a standard horn antenna (gray dash-dotted line) and of the same horn with a single SRR (black solid line), a MSRR (red dashed line) or two coupled SRRs (blue dotted line).

thumbnail Figure 9.

Normalized realized gain of a standard horn antenna (gray dash-dotted line) and of the same horn with a single SRR (black solid line), a MSRR (red dashed line) or two coupled SRRs (blue dotted line).

Moreover, by using the same approach, different metamaterial-inspired particles can be used. In fact, each of these has a different Q-factor and, thus, different frequency response in terms of fractional bandwidth. In particular, here we report the comparison between the SRR and a multiple-SRR (MSRR) or two coupled SRRs (C-SRRs), which are able to reduce or broaden the rejected band, respectively. The first one exhibits a higher Q-factor, due to its electrically smaller dimensions with respect to the conventional SRR, whereas the critical coupling between two properly spaced SRRs can be exploited for achieving a larger bandwidth compared to the one of a single resonator [37]. Therefore, as shown in Figures 8 and 9, we are able to obtain a different operation bandwidth depending on the used inclusion. In this way, the proposed approach can be employed in several systems characterized by different requirements in term of rejection bandwidth.

4 Conclusion

In this contribution, we have reviewed and discussed our recent results about signal manipulation process obtained through horn antennas loaded with metamaterial-inspired particles. In particular, we have shown that, depending on the used inclusion, a wideband horn antenna can be enabled to perform different manipulations on the transmitted and received signals, such as band-pass and band-stop filtering processes, and polarization transformation. Therefore, the proposed modules can be considered as a new family of microwave components that perform signal manipulation directly inside the radiating element of a communication system. By using these compact modules, we reduce the number of components constituting a communication system, with clear advantages in terms of cost, weight, complexity, and space occupancy.

Please, note that all the reported results have been obtained by using the full-wave simulator CST Microwave Studio [38]. In order to further confirm their effectiveness, most of the designed modules have been also manufactured and characterized both in terms of impedance matching and radiation performance. For the sake of brevity we have not reported the corresponding results, presented in [34–37], but we remark here that they are in good agreement with the simulated ones and confirm the different signal manipulation achievable with the proposed modules.

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Cite this article as: Barbuto M, Ramaccia D, Trotta F, Bilotti F & Toscano A: Signal manipulation through horn antennas loaded with metamaterial-inspired particles: A review. EPJ Appl. Metamat. 2015, 2, 5.

All Figures

thumbnail Figure 1.

Schematic block diagram of the proposed system.
In the text
thumbnail Figure 2.

Geometrical sketch of the band-pass filtering module working for linear polarization (a) and of the overall structure consisting of the filtering module inserted between a WR-62 waveguide connected to a pyramidal horn antenna (b).
In the text
thumbnail Figure 3.

Geometrical sketch of the band-pass filtering module working for circular polarization (a) and of the overall structure consisting of the filtering module inserted between a WR-62 waveguide connected to a corrugated conical horn antenna (b).
In the text
thumbnail Figure 4.

Reflection coefficient magnitude of a standard horn antenna (gray dash-dotted line) and of the same horn with a bi-omega particle (black solid line) or a CESR (red dashed line).
In the text
thumbnail Figure 5.

Normalized realized gain of a standard horn antenna (gray dash-dotted line) and of the same horn with a bi-omega particle (black solid line) or a CESR (red dashed line).
In the text
thumbnail Figure 6.

Axial ratio in the main beam direction of a horn antenna loaded with a CESR.
In the text
thumbnail Figure 7.

Geometrical sketch of the band-stop filtering modules consisting of a single SRR (a), a single MSRR (b), two coupled-SRRs (c) and of the overall structure consisting of the filtering module inserted between a WR-90 waveguide connected to a pyramidal horn antenna (d).
In the text
thumbnail Figure 8.

Reflection coefficient magnitude of a standard horn antenna (gray dash-dotted line) and of the same horn with a single SRR (black solid line), a MSRR (red dashed line) or two coupled SRRs (blue dotted line).
In the text
thumbnail Figure 9.

Normalized realized gain of a standard horn antenna (gray dash-dotted line) and of the same horn with a single SRR (black solid line), a MSRR (red dashed line) or two coupled SRRs (blue dotted line).
In the text

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